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Cx Family Common Mode Chokes

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XAL7050 High-inductance Shielded Power Inductors

XGL4020 Ultra-low DCR Power Inductors

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Design of switching power transformers can be accomplished in a relatively simple manner by limiting magnetic configurations to a few core and coilform structures. These structures have been chosen both for their versatility and their low cost. Dimensional information as well as design information in the form of design curves for the chosen structures may be found at the end of this document. By using these curves, the complete transformer can be designed.

The first step in the design is choosing a minimum structure size consistent with the output power required. The approximate power capabilities of each structure are provided in Table 1. If five or six outputs are required, a larger structure may be required to allow the copper along with insulation and winding crossovers to fit in the available winding area.

For a given core size, the ability of an inductor to operate without saturating is directly proportional to its turn count *N _{P}*. The normal saturation specification is

(1)

Where:

*E-T* = the minimum volt-time rating in volt-seconds

*B* = the maximum allowable flux density

*A _{E}* = the effective cross sectional core

Equation 1 is plotted for the specific chosen core structures shown in Figure 1. *These plots are for B* = 3000 Gauss, which will prevent the core from saturation and typically will provide low core loss suitable for operation in the range of 200 kHz to 400 kHz. For higher frequencies, a higher primary turn count should be used to ensure low core loss. To use this chart, locate the required *E-T* rating on the vertical axis. Move horizontally to the curve. From this point drop vertically to the horizontal axis and determine *N _{P}*. This value for

Secondary turn count is a function of duty cycle and primary turn count.

For a flyback system:

(2)

For a forward converter:

(3)

Where:

*N _{P}* = the primary turn count.

For the flyback system, *D* is seldom greater than 0.5. For the forward converter, *D* is the duty cycle of the rectified output, and can approach 0.9 for a wave rectified output. Known conditions should be used to calculate *N _{S}*. For example, at minimum input voltage and maximum output power, the supply will operate at maximum duty cycle. This is a good point to use to determine

Once all the turn counts have been determined, wire size must be chosen for each winding.

Power losses in the transformer windings cause a temperature rise, ∆T, in the transformer. The amount of loss depends on how much current is being drawn from the winding, the length of wire and what wire size is used. The power loss is a function of the amount of resistance in the wire. This resistance is composed of a DC resistance (*R _{DC}*) and an AC resistance (

In order to calculate the wire size, it is necessary to assign an acceptable power loss P_{L} to each winding. The power loss is then used to calculate the required DCR.

For flyback transformers:

(4)

For the forward converter:

(5)

Where:

*P _{L}* = the maximum allowable power loss in the winding.

Once *R _{DC}* for all the windings has been calculated, the wire size can be determined using the average length per turn (Table 1) for each coil form. Divide the

After the wire sizes have been determined, it is necessary to check fit, to see if the available winding area will accommodate the copper calculated in the previous steps. The available winding area for the structure chosen is shown in Table 1. The area each winding occupies must be determined, then the areas occupied by each winding are added. To this total, an area allowing for interwinding insulation should be added. Assume about 10% of the available area for insulation. The grand total is then compared to the available winding area. If the area of the windings is greater than the allowed structure area, either wire size must be reduced, or a larger structure must be chosen. Of course, a reduction in wire size results in increased losses in the transformer.

A fit of 100% of the available space should not be used. To accommodate winding crossovers, interwinding insulation and spaces between turns, it is recommended that a fit factor no greater than about 80% be used. For transformers with multiple outputs this factor may need to be reduced further.

To determine winding area, use the curves in Figure 2. From this chart the number of turns per layer *nl* can be read directly. Next find the number of layers, *l*, by dividing turns *N* by *nl*.

(6)

Next, find the area per layer, *al*. Multiply the winding width as shown on the individual coilform drawing (Figures 4 and 5) by the wire diameter. Multiply this value by the number of layers to find the area occupied by the winding.

(7)

Repeat this procedure for each winding and add to find the total area occupied by the windings.

(8)

The total winding area, *at*, added to the area of insulation and shielding if required, *ai*, must be less than the allowed structure area, *aw*.

(9)

For a forward converter it is generally preferable to have as much inductance as possible. For a flyback, however it is necessary to calculate the desired primary inductance based on the amount of energy stored per cycle (1/2 LI^{2}) required to deliver an average output power Po.

(10)

Where:

*L* = inductance

*η* = transformer efficiency (assume >0.9)

*V* = minimum DC input voltage applied to the primary

*t _{on}* = maximum on time for input voltage

Now that the structure size and winding turn counts have been found, the air gap must be determined. For most forward converters, inductance should be as large as possible and no air gap is required. However for flyback transformers and chokes, an air gap is necessary. For economic reasons and for the best reduction of EMI, cores are usually gapped in the center leg. The amount of gap can be found in Figure 3. To use this chart it is necessary to convert inductance, *L*, to inductance factor, *A _{L}*.

(11)

The transformer should now be ready to wind. Sufficient insulation must be used for the required voltage isolation. Windings must be uniform and carefully wound to minimize leakage inductance. Some small adjustments may be necessary to obtain the exact results desired, but this procedure will provide a good first draft design.

EP and EFD series cores have proven to be both versatile and cost effective for transformer design of about 50 Watts or less. EP cores are suitable for lower power and offer the smallest pcb area. EFD cores offer the lowest profile (height). The recommended core sizes are shown in Table 1.

*Table 1. Core Data*

EP7 | EP10 | EP13 | EFD15 | EFD17 | EFD20 | EFD25 | |
---|---|---|---|---|---|---|---|

Power capacity @ 100 kHz | 10 W | 12 W | 20 W | 20 W | 25 W | 30 W | 50 W |

a_{e} (effective cross-sectional area) – cm^{2} |
0.10 | 0.11 | 0.20 | 0.14 | 0.21 | 0.31 | 0.59 |

l_{e} (mean magnetic path length) – cm |
1.57 | 1.92 | 2.47 | 3.29 | 3.88 | 4.61 | 5.65 |

a_{w} (bobbin winding area) – cm^{2} |
0.045 | 0.122 | 0.141 | 0.173 | 0.198 | 0.286 | 0.4175 |

Required board space – mm | 13.2 × 10.9 | 15.2 × 12.7 | 17.8 × 13.5 | 22.0 × 17.2 | 24.1 × 17.4 | 30.0 × 20.6 | 32.7 × 26.8 |

Maximum height – mm | 9.0 | 11.0 | 12.3 | 8.5 | 10.0 | 11.4 | 14.0 |

Average length per turn – cm | 1.79 | 2.15 | 2.38 | 2.60 | 3.15 | 3.90 | 4.64 |

*Figure 1. Volt time product vs primary turns*

*Figure 2. Turns per layer vs wire size*

*Figure 3. Inductance factor vs air gap
*

Figure 5. EFD core dimensions

- Assistance with Safety Agency Approvals
- Basics of Inductor Selection (from Electronic Design magazine)
- Calibration, Compensation, and Correlation
- Current and Temperature Ratings
- Getting Started: An Introduction to Inductor Specifications
- Hipot Testing of Magnetic Components
- How Current and Power Relates to Losses and Temperature Rise
- Measuring Self Resonant Frequency
- Operating Voltage for Inductors
- Selecting Current Sensors and Transformers
- Simulation Model Considerations: Part I
- Simulation Model Considerations: Part II
- S-parameters for High-frequency Circuit Simulations
- Testing Inductors at Application Frequencies
- Working Voltage Ratings Applied to Inductors

- PCB Washing and Coilcraft Parts
- Selecting Flux for Soldering Coilcraft Components
- Soldering Surface Mount Components

- Broadband Chokes for Bias Tee Applications
- Inductors as RF Chokes
- Key Parameters for Selecting RF Inductors

- Beyond the Data Sheet: The Need for Smarter Power Inductor Specification Tools
- Choosing Inductors for Energy Efficient Power Applications
- Current Sense Transformers for Switched-mode Power Supplies
- Determining Inductor Power Losses
- Ferrite Vs Pressed Powder-core Inductors
- Forward or Flyback? Which is Better?
- Notes on Thermal Aging in Inductor Cores
- Selecting Coupled Inductors for SEPIC Applications
- Selecting Inductors to Drive LEDs
- Selecting the Best Inductor for Your DC-DC Converter
- Transformers for SiC FETs

- Coilcraft LC Filter Reference Design
- Common Mode Filter Design Guide
- Common Mode Filter Inductor Analysis
- Data Line Filtering
- Fundamentals of Electromagnetic Compliance
- Passive LC Filter Design and Analysis
- Selecting Common Mode Filter Chokes for High Speed Data Interfaces

- Applying Statistical Techniques to the Design of Custom Magnetics
- Choosing Power Inductors for LiDAR Systems
- Coilcraft Conical Inductors
- Designing a 9th Order Elliptical Filter for MoCA® Applications
- Measuring Sensitivity of Transponder Coils
- Power-handling Capabilities of Inductors
- Signal Transformer Application
- Transponder Coils in an RFID System
- Using Baluns and RF Components for Impedance Matching
- Using Standard Transformers in Multiple Applications